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power supply battery charger regulation control circuit the mc33341 is a monolithic regulation control circuit that is specifically designed to close the voltage and current feedback loops in power supply and battery charger applications. this device features the unique ability to perform source highside, load highside, source lowside and load lowside current sensing, each with either an internally fixed or externally adjustable threshold. the various current sensing modes are accomplished by a means of selectively using the internal differential amplifier, inverting amplifier, or a direct input path. positive voltage sensing is performed by an internal voltage amplifier. the voltage amplifier threshold is internally fixed and can be externally adjusted in all lowside current sensing applications. an active high drive output is provided to directly interface with economical optoisolators for isolated output power systems. this device is available in 8lead dualinline and surface mount packages. ? differential amplifier for highside source and load current sensing ? inverting amplifier for source return lowside current sensing ? noninverting input path for load lowside current sensing ? fixed or adjustable current threshold in all current sensing modes ? positive voltage sensing in all current sensing modes ? fixed voltage threshold in all current sensing modes ? adjustable voltage threshold in all lowside current sensing modes ? output driver directly interfaces with economical optoisolators ? operating voltage range of 2.3 v to 16 v representative block diagram this device contains 114 active transistors. 8 drive output 1 current sense input a 7 v cc 2 current threshold adjust 6 current sense input b/ voltage threshold adjust 3 compensation 5 voltage sense input 4 gnd differential amp inverting/ noninverting amp v i 0.2 v 1.2 v reference voltage and current transconductance amp/driver 1.0 1.0 on semiconductor ? semiconductor components industries, llc, 2001 august, 2001 rev. 2 1 publication order number: mc33341/d device operating temperature range package mc33341 semiconductor technical data power supply battery charger regulation control circuit ordering information mc33341d mc33341p t a = 25 to +85 c so8 plastic dip p suffix plastic package case 626 8 1 18 7 6 5 2 3 4 (top view) current sense input a current threshold adjust compensation drive output pin connections 8 1 d suffix plastic package case 751 (so8) gnd v cc current sense input b/ voltage threshold adjust voltage sense input
mc33341 http://onsemi.com 2 maximum ratings rating symbol value unit power supply voltage (pin 7) v cc 16 v voltage range current sense input a (pin 1) current threshold adjust (pin 2) compensation (pin 3) voltage sense input (pin 5) current sense input b/voltage threshold adjust (pin 6) drive output (pin 8) v ir 1.0 to v cc v drive output source current (pin 8) i source 50 ma thermal resistance, junctiontoair p suffix, dip plastic package, case 626 d suffix, so8 plastic package, case 751 r q ja 100 178 c/w operating junction temperature (note 1) t j 25 to +150 c storage temperature t stg 55 to +150 c note: esd data available upon request. electrical characteristics (v cc = 6.0 v, t a = 25 c, for min/max values t a is the operating junction temperature range that applies (note 1), unless otherwise noted.) characteristic symbol min typ max unit current sensing (pins 1, 2, 6) highside source and load sensing pin 1 to pin 6 (pin 1 >1.6 v) v th(i hs) mv internally fixed threshold voltage (pin 2 = v cc ) t a = 25 c 187 197 207 t a = t low to t high 183 211 externally adjusted threshold voltage (pin 2 = 0 v) 10 externally adjusted threshold voltage (pin 2 = 200 mv) 180 lowside load sensing pin 1 to pin 4 (pin 1 = 0 v to 0.8 v) v th(i ls+) mv internally fixed threshold voltage (pin 2 = v cc ) t a = 25 c 194 200 206 t a = t low to t high 192 208 externally adjusted threshold voltage (pin 2 = 0 v) 10 externally adjusted threshold voltage (pin 2 = 200 mv) 180 lowside source return sensing pin 1 to 4 (pin 1 = 0 v to 0.2 v) v th(i ls) mv internally fixed threshold voltage (pin 2 = v cc ) t a = 25 c 195 201 207 t a = t low to t high 193 209 externally adjusted threshold voltage (pin 2 = 0 v) 10 externally adjusted threshold voltage (pin 2 = 200 mv) 180 current sense input a (pin 1) input bias current, highside source and load sensing (pin 2 = 0 v to v pin 6 v) i ib(a hs) 40 m a input bias current, lowside load sensing (pin 2 = 0 v to 0.8 v) i ib(a ls+) 10 na input resistance, lowside source return sensing (pin 2 = 0.6 v to 0 v) r in(a ls) 10 k w current sense input b/voltage threshold adjust (pin 6) i ib(b) input bias current highside source and load current sensing (pin 6 > 2.0 v) 20 m a voltage threshold adjust (pin 6 < 1.2 v) 100 na current sense threshold adjust (pin 2) i ib(i th) 10 na input bias current transconductance, current sensing inputs to drive output g m(i) 6.0 mhos note: 1. tested ambient temperature range for the mc33341: t low = 25 c, t high = +85 c.
mc33341 http://onsemi.com 3 electrical characteristics (continued) (v cc = 6.0 v, t a = 25 c, for min/max values t a is the operating junction temperature range that applies (note 1), unless otherwise noted.) characteristic unit max typ min symbol differential amplifier disable logic (pins 1, 6) logic threshold voltage pin 1 (pin 6 = 0 v) v enabled, highside source and load current sensing v th(i hs) 1.7 disabled, lowside load and source return current sensing v th(i ls) 1.3 voltage sensing (pins 5, 6) positive sensing pin 5 to pin 4 v th(v) internally fixed threshold voltage t a = 25 c 1.186 1.210 1.234 v t a = t low to t high 1.174 1.246 v externally adjusted threshold voltage (pin 6 = 0 v) 40 mv externally adjusted threshold voltage (pin 6 = 1.2 v) 1.175 v voltage sense, input bias current (pin 5) i ib(v) 10 na transconductance, voltage sensing inputs to drive output g m(v) 7.0 mhos drive output (pin 8) high state source voltage (i source = 10 ma) v oh v cc 0.8 v high state source current (pin 8 = 0 v) i source 15 20 ma total device (pin 7) operating voltage range v cc 2.5 to 15 2.3 to 15 v power supply current (v cc = 6.0 v) i cc 300 600 m a note: 1. tested ambient temperature range for the mc33341: t low = 25 c, t high = +85 c. pin function description pin name description 1 current sense input a this multimode current sensing input can be used for either source highside, load highside, sourcereturn lowside, or load lowside sensing. it is common to a differential amplifier, inverting amplifier, and a noninverting input path. each of these sensing paths indirectly connect to the current sense input of the transconductance amplifier. this input is connected to the high potential side of a current sense resistor when used in source highside, load highside, or load lowside current sensing modes. in source return lowside current sensing mode, this pin connects to the low potential side of a current sense resistor. 2 current threshold adjust the current sense threshold can be externally adjusted over a range of 0 v to 200 mv with respect to pin 4, or internally fixed at 200 mv by connecting pin 2 to v cc . 3 compensation this pin is connected to a high impedance node within the transconductance amplifier and is made available for loop compensation. it can also be used as an input to directly control the drive output. an active low at this pin will force the drive output into a high state. 4 ground this pin is the regulation control ic ground. the control threshold voltages are with respect to this pin. 5 voltage sense input this is the voltage sensing input of the transconductance amplifier. it is normally connected to the power supply/battery charger output through a resistor divider. the input threshold is controlled by pin 6. 6 current sense input b/ voltage threshold adjust this is a dual function input that is used for either highside current sensing, or as a voltage threshold adjustment for pin 5. this input is connected to the low potential side of a current sense resistor when used in source highside or load highside current sensing modes. in all lowside current sensing modes, pin 6 is available as a voltage threshold adjustment for pin 5. the threshold can be externally adjusted over a range of 0 v to 1.2 v with respect to pin 4, or internally fixed at 1.2 v by connecting pin 6 to v cc . 7 v cc this is the positive supply voltage for the regulation control ic. the typical operating voltage range is 2.3 v to 15 v with respect to pin 4. 8 drive output this is a sourceonly output that normally connects to a linear or switching regulator control circuit. this output is capable of 15 ma, allowing it to directly drive an optoisolator in primary side control applications where galvanic isolation is required.
mc33341 http://onsemi.com 4 0 0 0 0 -50 1.0 0 280 0 1.6 -50 4.0 v pin 2 , current threshold adjust (mv) v pin 2 , current threshold adjust (v) t a , ambient temperature ( c) v pin 2 , current threshold adjust (mv) v pin 6 , voltage threshold adjust (v) figure 1. voltage sensing threshold change versus temperature t a , ambient temperature ( c) figure 2. current sensing threshold change versus temperature v cc = 6.0 v figure 3. closedloop voltage sensing input versus voltage threshold adjust figure 4. closedloop current sense input b versus current threshold adjust figure 5. closedloop current sensing input a versus current threshold adjust figure 6. closedloop current sensing input a versus current threshold adjust -25 0 25 50 75 100 125 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 40 80 120 160 200 240 280 -25 0 25 50 75 100 125 40 80 120 160 200 240 280 40 80 120 160 200 240 280 0 -4.0 -8.0 -12 0 -1.0 -2.0 -3.0 -40 -80 -120 -160 -200 -240 -280 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0 240 200 160 120 80 40 0 -40 -80 -120 -160 -200 -240 -260 16 14 12 10 8.0 6.0 4.0 2.0 0 0 2.0 4.0 6.0 8.0 10 12 14 14 12 10 8.0 6.0 4.0 2.0 0 14 12 10 8.0 6.0 4.0 2.0 0 v cc = 6.0 v 1 - source high-side and load high-side 2 - source return low-side 3 - load low-side v cc v cc = 6.0 v v o = 1.0 v i o = 1.0 ma t a = 25 c 1 2 3 v pin 5 v pin 6 -v pin 5 v pin 6 v pin 1 -v pin 6 v cc = 6.0 v v o = 1.0 v i o = 1.0 ma pin 1 = v cc t a = 25 c gnd v pin 5 v pin 2 -v pin 1 v cc = 6.0 v v o = 1.0 v i o = 1.0 ma t a = 25 c v pin 2 -|v pin 1 | v pin 5 v cc = 6.0 v v o = 1.0 v i o = 1.0 ma t a = 25 c noninverting input path is active for load low-side current sensing. inverting amplifier is active for source return low-side current sensing. gnd v v pin 5 , voltage sensing input (v) th(i hs) , current sensing d v d th(v) , voltage sensing threshold change (mv) threshold change (mv) v pin 6 , current sense input b (mv) v pin 1 , current sense input a (mv) v pin 2 -v pin 1 , input difference voltage (mv) v pin 1 , current sense input a (mv) v pin 6 -v pin 5 , input difference voltage (mv) v pin 1 -v pin 6 , input difference voltage (mv) v pin 2 -|v pin 1 |, input difference voltage (mv) differential amplifier is active for source high-side and load high-side current sensing. both vertical axis are expressed in millivolts down to v cc .
mc33341 http://onsemi.com 5 0 1.0 0.1 8.0 1.0 k 60 0 0 0.1 8.0 1.0 k 60 v cc , supply voltage (v) i o , drive output load current (ma) f, frequency (hz) i l , output load current (ma) i o , drive output load current (ma) figure 7. bode plot voltage sensing inputs to drive output f, frequency (hz) figure 8. bode plot current sensing inputs to drive output figure 9. transconductance voltage sensing inputs to drive output figure 10. transconductance current sensing inputs to drive output figure 11. drive output high state source saturation versus load current figure 12. supply current versus supply voltage v cc = 6.0 v v o = 1.0 v r l = 1.0 k pin 3 = 1.0 nf t a = 25 c v cc = 6.0 v v o = 1.0 v r l = 1.0 k pin 3 = 1.8 nf t a = 25 c v cc = 6.0 v v o = 1.0 v t a = 25 c v cc = 6.0 v v o = 1.0 v t a = 25 c v cc = 6.0 v t a = 25 c i o = 0 ma t a = 25 c gain phase gain phase high-side sensing phase low-side sensing drive output low state 10 k 10 k 100 k 1.0 m 100 k 1.0 m 0.2 0.3 0.5 1.0 2.0 3.0 5.0 10 0.2 0.3 0.5 1.0 2.0 3.0 5.0 10 4.0 8.0 12 16 20 4.0 8.0 12 16 50 40 30 20 10 0 50 40 30 20 10 0 6.0 4.0 2.0 0 6.0 4.0 2.0 0 -0.4 -0.8 -1.2 -1.6 -2.0 0.8 0.6 0.4 0.2 0 180 160 140 120 100 80 180 160 140 120 100 80 a vol(i) , current sensing open-loop f , excess phase ( ) voltage gain (db) a vol(v) , voltage sensing open-loop voltage gain (db) g m(v) , voltage sensing transconductance (mhos) g m(i) , current sensing transconductance (mhos) v oh , output source saturation voltage (v) f , excess phase ( ) i cc , supply current, drive output low state (ma) v cc drive output high state
mc33341 http://onsemi.com 6 introduction power supplies and battery chargers require precise control of output voltage and current in order to prevent catastrophic damage to the system load. many present day power sources contain a wide assortment of building blocks and glue devices to perform the required sensing for proper regulation. typical feedback loop circuits may consist of a voltage and current amplifier, level shifting circuitry, summing circuitry and a reference. the mc33341 contains all of these basic functions in a manner that is easily adaptable to many of the various power sourceload configurations. operating description the mc33341 is an analog regulation control circuit that is specifically designed to simultaneously close the voltage and current feedback loops in power supply and battery charger applications. this device can control the feedback loop in either constantvoltage or constantcurrent mode with automatic crossover. a concise description of the integrated circuit blocks is given below. refer to the block diagram in figure 13. transconductance amplifier a quad input transconductance amplifier is used to control the feedback loop. this amplifier has separate voltage and current channels, each with a sense and a threshold input. within a given channel, if the sense input level exceeds that of the threshold input, the amplifier output is driven high. the channel with the largest difference between the sense and threshold inputs will set the output source current of the amplifier and thus dominate control of the feedback loop. the amplifier output appears at pin 8 and is a sourceonly type that is capable of 15 ma. a high impedance node within the transconductance amplifier is made available at pin 3 for loop compensation. this pin can sink and source up to 10 m a of current. system stability is achieved by connecting a capacitor from pin 3 to ground. the compensation pin signal is out of phase with respect to the drive output. by actively clamping pin 3 low, the drive output is forced into a high state. this, in effect, will shutdown the power supply or battery charger, by forcing the output voltage and current regulation threshold down towards zero. voltage sensing the voltage that appears across the load is monitored by the noninverting v sen input of the transconductance amplifier. this voltage is resistively scaled down and connected to pin 5. the threshold at which voltage regulation occurs is set by the level present at the inverting v th input of the transconductance amplifier. this level is controlled by pin 6. in source highside and load highside current sensing modes, pin 6 must be connected to the low potential side of current sense resistor r s . under these conditions, the voltage regulation threshold is internally fixed at 1.2 v. in source return lowside and load lowside current sensing modes, pin 6 is available, and can be used to lower the regulation threshold of pin 5. this threshold can be externally adjusted over a range of 0 v to 1.2 v with respect to the ic ground at pin 4. current sensing current sensing is accomplished by monitoring the voltage that appears across sense resistor r s, level shifting it with respect to pin 4 if required, and applying it to the noninverting i sen input of the transconductance amplifier. in order to allow for maximum circuit flexibility, there are three methods of current sensing, each with different internal paths. in source highside (figures 13 and 14) and load highside (figures 17 and 18) current sensing, the differential amplifier is active with a gain of 1.0. pin 1 connects to the high potential side of current sense resistor r s while pin 6 connects to the low side. logic circuitry is provided to disable the differential amplifier output whenever lowside current sensing is required. this circuit clamps the differential amplifier output high which disconnects it from the i sen input of the transconductance amplifier. this happens if pin 1 is less than 1.2 v or if pin 1 is less than pin 6. with source return lowside current sensing (figures 15 and 16), the inverting amplifier is active with a gain of 1.0. pin 1 connects to the low potential side of current sense resistor r s while pin 4 connects to the high side. note that a negative voltage appears across r s with respect to pin 4. in load lowside current sensing (figures 19 and 20) a noninverting input path is active with a gain of 1.0. pin 1 connects to the high potential side of current sense resistor r s while pin 4 connects to the low side. the noninverting input path lies from pin 1, through the inverting amplifier input and feedback resistors r, to the cathode of the output diode. with load lowside current sensing, pin 1 will be more positive than pin 4, forcing the inverting amplifier output low. this causes the diode to be reverse biased, thus preventing the output stage of the amplifier from loading the input signal that is flowing through the feedback resistors. the regulation threshold in all of the current sensing modes is internally fixed at 200 mv with pin 2 connected to v cc . pin 2 can be used to externally adjust the threshold over a range of 0 to 200 mv with respect to the ic ground at pin 4. reference an internal band gap reference is used to set the 1.2 v voltage threshold and 200 mv current threshold. the reference is initially trimmed to a 1.0% tolerance at t a = 25 c and is guaranteed to be within 2.0% over an ambient operating temperature range of 25 to 85 c. applications each of the application circuits illustrate the flexibility of this device. the circuits shown in figures 13 through 20 contain an optoisolator connected from the drive output at
mc33341 http://onsemi.com 7 pin 8 to ground. this configuration is shown for ease of understanding and would normally be used to provide an isolated control signal to a primary side switching regulator controller. in nonisolated, primary or secondary side applications, a load resistor can be placed from pin 8 to ground. this resistor will convert the drive output current to a voltage for direct control of a regulator. in applications where excessively high peak currents are possible from the source or load, the load induced voltage drop across r s could exceed 1.6 v. depending upon the current sensing configuration used, this will result in forward biasing of either the internal v cc clamp diode, pin 6, or the device substrate, pin 1. under these conditions, input series resistor r3 is required. the peak input current should be limited to 20 ma. excessively large values for r3 will degrade the current sensing accuracy. figure 21 shows a method of bounding the voltage drop across r s without sacrificing current sensing accuracy. figure 13. source highside current sensing with internally fixed voltage and current thresholds r s load r1 battery or resistive load source return source r2 r3 comp the above figure shows the mc33341 configured for source highside current sensing allowing a common ground path between load and source return . the differential amplifier inputs, pins 1 and 6, are used to sense the load induced voltage drop that appears across resistor r s . the internal voltage and current regulation thresholds are selected by the respective external connections of pins 2 and 6. r esistor r3 is required in applications where a high peak level of reverse current is possible if the source inputs are shorted. the resist or value should be chosen to limit the input current of the internal v cc clamp diode to less than 20 ma. excessively large values for r3 will degrade the current sensing accuracy. v reg v th(v) r2 r1 1 1.2 r2 r1 1 i reg v th(ihs) r s 0.2 r s r3 i pk r s 0.6 0.02 v i load 8765 1234 r r r r r v cc v cc v cc v cc v cc v cc 0.4 v 1.2 v r 0.2 v v cc 0.2 v 0.4 v 1.2 v v cc 1.2 v v cc inverting amp transconductance amp differential amp disable logic differential amp opto isolator v sen v th i sen i th reference
mc33341 http://onsemi.com 8 r s load r1 battery or resistive load source return source r2 r3 comp the above figure shows the mc33341 configured for source highside current sensing with an externally adjustable current thresh old. operation of this circuit is similar to that of figure 13. the current regulation threshold can be adjusted over a range of 0 v to 200 mv with respect to pin 4. v i load 8765 1234 r r r r r v cc v cc v cc v cc v cc v cc 0.4 v 1.2 v r 0.2 v v cc 0.2 v 0.4 v 1.2 v v cc 1.2 v v cc inverting amp transconductance amp differential amp disable logic differential amp opto isolator v sen v th i sen i th reference figure 14. source highside current sensing with externally adjustable current and internally fixed voltage thresholds v reg v th(v) r2 r1 1 1.2 r2 r1 1 i reg v th(pin2) r s r3 i pk r s 0.6 0.02 current control
mc33341 http://onsemi.com 9 r s load r1 battery or resistive load source return source r2 r3 comp the above figure shows the mc33341 configured for source return lowside current sensing allowing a common power path between source + and load +. this configuration is especially suited for negative output applications where a common ground path, sourc e + to load +, is desired. the inverting amplifier inputs, pins 1 and 4, are used to sense the load induced voltage drop that appears across resi stor r s . the internal voltage and current regulation thresholds are selected by the respective external connections of pins 2 and 6. r esistor r3 is required in applications where high peak levels of inrush current are possible. the resistor value should be chosen to limit the negative substrate current to less than 20 ma. excessively large values for r3 will degrade the current sensing accuracy. v i load 8765 1234 r r r r r v cc v cc v cc v cc v cc v cc 0.4 v 1.2 v r 0.2 v v cc 0.2 v 0.4 v 1.2 v v cc 1.2 v v cc inverting amp transconductance amp differential amp disable logic differential amp opto isolator v sen v th i sen i th reference figure 15. source return lowside current sensing with internally fixed current and voltage thresholds v reg v th(v) r2 r1 1 1.2 r2 r1 1 i reg v th(ils) r s 0.2 r s r3 i pk r s 0.6 0.02
mc33341 http://onsemi.com 10 r s load r1 battery or resistive load source return source r2 r3 comp the above figure shows the mc33341 configured for source return lowside current sensing with externally adjustable voltage and current thresholds. operation of this circuit is similar to that of figure 15. the respective voltage and current regulation threshold can be adjusted over a range of 0 to 1.6 v and 0 v to 200 mv with respect to pin 4. v i load 8765 1234 r r r r r v cc v cc v cc v cc v cc v cc 0.4 v 1.2 v r 0.2 v v cc 0.2 v 0.4 v 1.2 v v cc 1.2 v v cc inverting amp transconductance amp differential amp disable logic differential amp opto isolator v sen v th i sen i th reference figure 16. source return lowside current sensing with externally adjustable current and voltage thresholds v reg v th(pin6) r2 r1 1 i reg v th(pin2) r s r3 i pk r s 0.6 0.02 voltage control current control
mc33341 http://onsemi.com 11 r3 load r1 battery or resistive load source return source r2 r s comp the above figure shows the mc33341 configured for load highside current sensing allowing common paths for both power and groun d, between the source and load. the differential amplifier inputs, pins 1 and 6, are used to sense the load induced voltage drop t hat appears across resistor r s . the internal voltage and current regulation thresholds are selected by the respective external connections of pins 2 and 6. resistor r3 is required in applications where high peak levels of load current are possible from the battery or load bypass capacitor. the resistor value should be chosen to limit the input current of the internal v cc clamp diode to less than 20 ma. excessively large values for r3 ill degrade the current sensing accuracy. v reg v th(v) r2 r1 1 1.2 r2 r1 1 i reg v th(ihs) r s 0.2 r s r3 i pk r s 0.6 0.02 v i load 8765 1234 r r r r r v cc v cc v cc v cc v cc v cc 0.4 v 1.2 v r 0.2 v v cc 0.2 v 0.4 v 1.2 v v cc 1.2 v v cc inverting amp transconductance amp differential amp disable logic differential amp opto isolator v sen v th i sen i th reference figure 17. load highside current sensing with internally fixed current and voltage thresholds
mc33341 http://onsemi.com 12 r3 load r1 battery or resistive load source return source r2 r s comp the above figure shows the mc33341 configured for load highside current sensing with an externally adjustable current threshol d. opera- tion of this circuit is similar to that of figure 17. the current regulation threshold can be adjusted over a range of 0 v to 2 00 mv with respect to pin 4. v reg v th(v) r2 r1 1 1.2 r2 r1 1 i reg v th(pin2) r s r3 i pk r s 0.6 0.02 v i load 8765 1234 r r r r r v cc v cc v cc v cc v cc v cc 0.4 v 1.2 v r 0.2 v v cc 0.2 v 0.4 v 1.2 v v cc 1.2 v v cc inverting amp transconductance amp differential amp disable logic differential amp opto isolator v sen v th i sen i th reference figure 18. load highside current sensing with externally adjustable current and internally fixed voltage thresholds current control
mc33341 http://onsemi.com 13 r3 load r1 battery or resistive load source return source r2 r s comp the above figure shows the mc33341 configured for load lowside current sensing allowing common paths for both power and ground , between the source and load. the noninverting input paths, pins 1 and 4, are used to sense the load induced voltage drop that a ppears across resistor r s . the internal voltage and current regulation thresholds are selected by the respective external connections of pins 2 and 6. resistor r3 is required in applications where high peak levels of load current are possible from the battery or load bypass capacitor. the resistor value should be chosen to limit the negative substratecurrent to less than 20 ma. excessively large values for r3 will degrade the current sensing accuracy. v reg v th(v) r2 r1 1 1.2 r2 r1 1 i reg v th(ils ) r s 0.2 r s r3 i pk r s 0.6 0.02 v i load 8765 1234 r r r r r v cc v cc v cc v cc v cc v cc 0.4 v 1.2 v r 0.2 v v cc 0.2 v 0.4 v 1.2 v v cc 1.2 v v cc inverting amp transconductance amp differential amp disable logic differential amp opto isolator v sen v th i sen i th reference figure 19. load lowside current sensing with internally fixed current and voltage thresholds
mc33341 http://onsemi.com 14 r3 load r1 battery or resistive load source return source r2 r s comp the above figure shows the mc33341 configured for load lowside current sensing with an externally adjustable voltage and curre nt threshold. operation of this circuit is similar to that of figure 19. the respective voltage and current regulation threshold c an be adjusted over a range of 0 to 1.2 v and 0 v to 200 mv, with respect to pin 4. v i load 8765 1234 r r r r r v cc v cc v cc v cc v cc v cc 0.4 v 1.2 v r 0.2 v v cc 0.2 v 0.4 v 1.2 v v cc 1.2 v v cc inverting amp transconductance amp differential amp disable logic differential amp opto isolator v sen v th i sen i th reference figure 20. load lowside current sensing with externally adjustable current and voltage thresholds v reg v th(pin6) r2 r1 1 i reg v th(pin2) r s r3 i pk r s 0.6 0.02 current control voltage current
mc33341 http://onsemi.com 15 load source source load 1 8765 234 mc33341 figure 21. current sense resistor bounding figure 22. multiple output current and voltage regulation source source return load load output short 1 8765 234 input short r s mc33341 note: an excessive load induced voltage across r s can occur if either the source input or load output is shorted. this voltage can easily be bounded with the addition of the diodes shown without degrading the current sensing accuracy. this bounding technique can be used in any of the mc33341 applications where high peak currents are anticipated. note: multiple outputs can be controlled by summing the error signal into a common optoisolator. the converter output with the larges t voltage or current error will dominate control of the feedback loop. source return load 1 8765 234 mc33341 output 2 output 1 output common opto isolator
mc33341 http://onsemi.com 16 figure 23. 10 v/1.0 a constantvoltage constantcurrent regulator figure 24. output load regulation figure 23 shows the mc33341 configured as a source highside constantvoltage constantcurrent regulator. the regulator is desi gned for an output voltage of 10 v at 1.0 a. figure 24 shows the regulator's output characteristics as the load is varied. source return lowside, load highside, and load lowside configurations will each exhibit a nearly identical load regulation characteristic. a heatsink is required for the mtp2955 series pass element. 11.1 k variable resistive load 82.5 k 0.01 v i output ground 8765 1234 r r r r r v cc v cc v cc v cc v cc v cc 0.4 v 1.2 v r 0.2 v v cc 0.2 v 0.4 v 1.2 v v cc 1.2 v v cc inverting amp transconductance amp differential amp disable logic differential amp v sen v th i sen i th reference 0 10 i o , output load current (a) 0.2 0 4 0.6 0.8 1.0 8.0 6.0 4.0 2.0 0 v o , output voltage (v) 10 3.0 k 10 0.2 mtp2955 output 10 v/1.0 a input ground input 12 v to 16 v
mc33341 http://onsemi.com 17 figure 25. constantcurrent constantvoltage switch mode charger figure 25 shows that the mc33341 can be configured as a highside constantcurrent constantvoltage switch mode charger. this c ircuit operates as a step down converter. with a nominal input voltage and output load current as stated above, the switching frequenc y is approximately 28 khz with and an associated conversion efficiency of 86 percent. the switching frequency will vary with changes in input voltage and load current. 12 k 68 k v i output ground 8765 1234 r r r r r v cc v cc v cc v cc v cc v cc 0.4 v 1.2 v r 0.2 v v cc 0.2 v 0.4 v 1.2 v v cc 1.2 v v cc inverting amp transconductance amp differential amp disable logic differential amp v sen v th i sen i th reference 100 mtp2955 output 5.87 v/800 ma input ground input 12 v 100 1n5821 0.25 3.0 k 200 m h
mc33341 http://onsemi.com 18 package dimensions p suffix plastic package case 62605 issue l notes: 1. dimension l to center of lead when formed parallel. 2. package contour optional (round or square corners). 3. dimensioning and tolerancing per ansi y14.5m, 1982. 14 5 8 f note 2 a b t seating plane h j g d k n c l m m a m 0.13 (0.005) b m t dim min max min max inches millimeters a 9.40 10.16 0.370 0.400 b 6.10 6.60 0.240 0.260 c 3.94 4.45 0.155 0.175 d 0.38 0.51 0.015 0.020 f 1.02 1.78 0.040 0.070 g 2.54 bsc 0.100 bsc h 0.76 1.27 0.030 0.050 j 0.20 0.30 0.008 0.012 k 2.92 3.43 0.115 0.135 l 7.62 bsc 0.300 bsc m --- 10 --- 10 n 0.76 1.01 0.030 0.040
mc33341 http://onsemi.com 19 package dimensions d suffix plastic package case 75107 issue w seating plane 1 4 5 8 n j x 45 k notes: 1. dimensioning and tolerancing per ansi y14.5m, 1982. 2. controlling dimension: millimeter. 3. dimension a and b do not include mold protrusion. 4. maximum mold protrusion 0.15 (0.006) per side. 5. dimension d does not include dambar protrusion. allowable dambar protrusion shall be 0.127 (0.005) total in excess of the d dimension at maximum material condition. a b s d h c 0.10 (0.004) dim a min max min max inches 4.80 5.00 0.189 0.197 millimeters b 3.80 4.00 0.150 0.157 c 1.35 1.75 0.053 0.069 d 0.33 0.51 0.013 0.020 g 1.27 bsc 0.050 bsc h 0.10 0.25 0.004 0.010 j 0.19 0.25 0.007 0.010 k 0.40 1.27 0.016 0.050 m 0 8 0 8 n 0.25 0.50 0.010 0.020 s 5.80 6.20 0.228 0.244 x y g m y m 0.25 (0.010) z y m 0.25 (0.010) z s x s m
mc33341 http://onsemi.com 20 on semiconductor and are trademarks of semiconductor components industries, llc (scillc). scillc reserves the right to make changes without further notice to any products herein. scillc makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does scillc assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. atypicalo parameters which may be provided in scill c data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. all operating parameters, including atypicalso must be validated for each customer application by customer's technical experts. scillc does not convey any license under its patent rights nor the rights of others. scillc products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body , or other applications intended to support or sustain life, or for any other application in which the failure of the scillc product could create a sit uation where personal injury or death may occur. should buyer purchase or use scillc products for any such unintended or unauthorized application, buyer shall indemnify and hold scillc and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthori zed use, even if such claim alleges that scillc was negligent regarding the design or manufacture of the part. scillc is an equal opportunity/affirmative action employer. publication ordering information japan : on semiconductor, japan customer focus center 4321 nishigotanda, shinagawaku, tokyo, japan 1410031 phone : 81357402700 email : r14525@onsemi.com on semiconductor website : http://onsemi.com for additional information, please contact your local sales representative. mc33341/d literature fulfillment : literature distribution center for on semiconductor p.o. box 5163, denver, colorado 80217 usa phone : 3036752175 or 8003443860 toll free usa/canada fax : 3036752176 or 8003443867 toll free usa/canada email : onlit@hibbertco.com n. american technical support : 8002829855 toll free usa/canada

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